Rec. ITUR P.6803
RECOMMENDATION ITUR P.6803
PROPAGATION DATA REQUIRED FOR THE DESIGN
OF EARTHSPACE MARITIME MOBILE
TELECOMMUNICATION SYSTEMS
(Question ITUR 207/3)
(1990199219971999)
Rec. ITUR P.6803
The ITU Radiocommunication Assembly,
considering
a) that for the proper planning of Earthspace maritime mobile systems it is necessary to have appropriate propagation data and prediction methods;
b) that the methods of Recommendation ITU R P.618 are recommended for the planning of Earthspace telecommunication systems;
c) that further development of prediction methods for specific application to maritime mobilesatellite systems is required to give adequate accuracy for all operational conditions;
d) that, however, methods are available which yield sufficient accuracy for many applications,
recommends
1 that the current methods set out in Annex 1 be adopted for use in the planning of Earthspace maritime mobile telecommunication systems, in addition to the methods recommended in Recommendation ITUR P.618.
ANNEX 1
1 Introduction
Telecommunications over Earthspace links for maritime mobilesatellite systems lead to propagation problems that are substantially different from those arising in the fixedsatellite service. For instance, the effects of reflections and scattering by the sea surface can be quite severe, in particular where antennas with wide beamwidths are used. Furthermore, maritime mobilesatellite systems may operate on a worldwide basis, including paths with low elevation angles.
This Annex deals with data and models specifically needed to characterize the seaspace path impairments which include:
– tropospheric effects, including rain attenuation, gaseous absorption, refraction, scintillation and anomalous propagation occurring at low elevation angles;
– ionospheric effects such as scintillation and Faraday rotation;
– surface reflection effects (multipath due to secondary paths arising from the reflection of radio waves from the sea surface);
– local environment effects (ship motion and sea conditions);
– interference effects due to differential fading between a desired signal and an interference signal, both affected by multipath fading.
2 Tropospheric effects 2.1 Attenuation
Signal losses in the troposphere are caused by atmospheric gases, rain, fog and clouds. Except at low elevation angles, tropospheric attenuation is negligible at frequencies below about 1 GHz, and is generally small at frequencies up to about 10 GHz. Above 10 GHz, the attenuation can be large for significant percentages of the time on many paths.
Prediction methods are available for estimating gaseous absorption (see Recommendation ITUR P.676) and rain attenuation (see Recommendation ITUR P.618). Fog and cloud attenuation is usually negligible for frequencies up to 10 GHz.
2.2 Scintillation
Irregular variations in received signal level and in angle of arrival are caused by both tropospheric turbulence and atmospheric multipath. The magnitudes of these effects increase with increasing frequency and decreasing path elevation angle, except that angle of arrival fluctuations caused by turbulence are independent of frequency. Antenna beamwidth also affects the magnitude of these scintillations. These effects are observed to be at a maximum in the summer season. A prediction method is given in Recommendation ITUR P.618.
3 Ionospheric effects
Ionospheric effects (see Recommendation ITUR P.531) may be important, particularly at frequencies below 1 GHz. For convenience these have been quantified for frequencies of 0.1, 0.25, 0.5, 1, 3 and 10 GHz in Table 1 for a high value of total electron content (TEC).
3.1 Ionospheric scintillation
Inhomogeneities of electron density in the ionosphere cause refractive focusing or defocusing of radio waves and lead to amplitude fluctuations termed scintillations. Ionospheric scintillation is maximum near the geomagnetic equator and smallest in the midlatitude regions. The auroral zones are also regions of large scintillation. Strong scintillation is Rayleigh distributed in amplitude; weaker scintillation is nearly lognormal. These fluctuations decrease with increasing frequency and depend upon path geometry, location, season, solar activity and local time. Table 2 tabulates fade depth data for VHF and UHF in midlatitudes, based on data in Recommendation ITUR P.531.
Accompanying the amplitude fluctuation is also a phase fluctuation. The spectral density of the phase fluctuation is proportional to 1/f ^{3}, where f is the Fourier frequency of the fluctuation. This spectral characteristic is similar to that arising from flicker of frequency in oscillators and can cause significant degradation to the performance of receiver hardware.
3.2 Faraday rotation
A linearly polarized wave propagating through the ionosphere undergoes a progressive rotation of the plane of polarization. Effects are summarized in Table 1.
The axial ratio of an incident elliptically polarized wave may be increased or decreased upon reflection (particularly at small angles) since Faraday rotation varies the orientation of the principal polarization axis of the incident wave. This results from the difference in reflection coefficient to be expected between vertical and horizontal components in most multipath situations.
The effects of Faraday rotation on wideband signals can be of significance to system performance. The differential rotation effects cannot be fully corrected at VHF by reorientation of the antenna axis of a linearly polarized antenna. On circularly polarized antennas, the effect is to introduce differential phase shifts of signal components across the band. Thus, signal components separated in frequency may be expected to be subject to frequency and phase selective distortion.
TABLE 1
Estimated^{*} ionospheric effects for elevation angles of about 30° oneway traversal^{**}
(derived from Recommendation ITUR P.531)
Effect

Frequency
dependence

0.1 GHz

0.25 GHz

0.5 GHz

1 GHz

3 GHz

10 GHz

Faraday rotation

1/ ^{2}

30 rotations

4.8 rotations

1.2 rotations

108

12

1.1

Propagation delay

1/ ^{2}

25 s

4 s

1 s

0.25 s

0.028 s

0.0025 s

Refraction

1/ ^{2}

1

0.16

2.4

0.6

4.2

0.36

Variation in the direction of
arrival (r.m.s.)

1/ ^{2}

20

3.2

48

12

1.32

0.12

Absorption (auroral and/or
polar cap)

1/ ^{2}

5 dB

0.8 dB

0.2 dB

0.05 dB

6 10^{–} ^{3} dB

5 10^{–} ^{4} dB

Absorption (midlatitude)

1/ ^{2}

1 dB

0.16 dB

0.04 dB

0.01 dB

< 0.001 dB

< 10^{–} ^{4} dB

Dispersion

1/ ^{3}

0.4 ps/Hz

0.026 ps/Hz

0.0032 ps/Hz

0.0004 ps/Hz

1.5 10^{–} ^{5} ps/Hz

4 10^{–} ^{7} ps/Hz

Scintillation ^{(1)}

See Rec.
ITUR.P.531

See Rec.
ITUR P.531

See Rec.
ITUR P.531

See Rec.
ITUR P.531

20 dB
peaktopeak

10 dB
peaktopeak

4 dB
peaktopeak

^{*} This estimate is based on a TEC of 10^{18} electrons/m^{2}, which is a high value of TEC encountered at low latitudes in daytime with high solar activity.
^{**} Ionospheric effects above 10 GHz are negligible.
^{(1)} Values observed near the geomagnetic equator during the early nighttime hours (local time) at equinox under conditions of high sunspot number.

TABLE 2
Distribution of midlatitude fade depths due to ionospheric scintillation (dB)
Percentage of time

Frequency
(GHz)

(%)

0.1

0.2

0.5

1

1.0

5.9

1.5

0.2

0.1

0.5

9.3

2.3

0.4

0.1

0.2

16.6

4.2

0.7

0.2

0.1

25.0

6.2

1.0

0.3

4 Fading due to sea reflection 4.1 Fading depth
The following simple method provides approximate estimates of multipath power or fading depth suitable for many engineering applications.
Applicable conditions:
Frequency range: 0.88 GHz
Elevation angle: 5 _{i} 20
where G() is the antenna radiation pattern of the main lobe given by:
(1)
where:
G_{m} : value of the maximum antenna gain (dBi)
: angle measured from boresight (degrees)
Polarization: circular
Sea condition: wave height of 13 m (incoherent component fully developed).
Step 1: Find the relative antenna gain G in the direction of the point of specular reflection. The relative antenna gain is approximated by equation (1) where 2 _{i} (degrees).
Step 2: Calculate the Fresnel reflection coefficient of the sea for circular polarization, R_{C}_{ }:
(circular polarization) (2a)
where:
(horizontal polarization) (2b)
(vertical polarization) (2c)
and
where:
_{r} () : relative permittivity of the surface at frequency f (from Recommendation ITUR P.527)
() : conductivity (S/m) of the surface at frequency f (from Recommendation ITUR P.527)
: free space wavelength (m).
A set of curves is given in Fig. 1 for the magnitude of the Fresnel reflection coefficient of sea for circular polarization for five frequencies between 0.8 GHz and 8 GHz. The curves are obtained from equation (2) with the electrical parameters corresponding to average salinity sea water.
Step 3: Find the normalized diffuse coefficient (ratio of diffuse component of reflectiontoreflection coefficient for calm sea condition), _{I} (dB), from Fig. 2.
FIGURE 1..[068001]
FIGURE 2..[068002]
Step 4: The mean incoherent power of sea reflected waves relative to the direct wave, P_{r} , is given by:
P_{r} G R _{I} dB (3)
where:
R 20 log R_{C} dB (3a)
with R_{C} from equation (2).
Step 5: Assuming the NakagamiRice distribution, fading depth is estimated from:
(4)
where A is the amplitude (dB) read from the ordinate of Fig. 3.
FIGURE 3..[068003] = xx cm
4.2 Frequency spectrum and fade duration statistics
In general, spectral bandwidth increases with increasing wave height, elevation angle, ship velocity, and the relative motion of the shipborne antenna (rolling/pitching). The dependence of the spectral shape on antenna polarization is small, and the dependence on antenna gain is weak for gains less than about 10 dB.
The – 10 dB spectral bandwidth, f_{–}_{ }_{10}, is defined as the bandwidth over which the power density decays to – 10 dB relative to the peak power density. Figure 4 shows the probable range of the 10 dB spectral bandwidth of 1.5 GHz multipath fading obtained by a theoretical fading model as a function of the elevation angle under conditions typical of maritime satellite communications (significant wave height of 15 m, ship speed of 020 knots and rolling of 030).
FIGURE 4..[068004] = xx cm
Average values of fade duration, T_{D}, and fade occurrence interval, T_{I} defined in Fig. 5 can be obtained by the following procedure by using the – 10 dB spectral bandwidth, f_{–}_{ }_{10}:
T_{I} ( p) < T_{I} (50%) exp [m( p)^{2} / 2]
T_{D} ( p) < T_{I} ( p) ( 1 – p / 100)
where:
Predicted values of T_{D} and T_{I} for 99% of the time at elevation angles from 5 to 10 are 0.05 to 0.4 s for T_{D} and 5 to 40 s for T_{I}
The probability density function of T_{D} and T_{I} at any time percentage ranging from 50% to 99% is approximately an exponential distribution.
5 Interference from adjacent satellite systems 5.1 General
In mobilesatellite communication systems, amplitudes of the desired signal from the satellite and an interfering signal from an adjacent satellite experience independent level fluctuations due to multipath fading, requiring a different treatment from that of fixedsatellite systems. A main point to be considered is the statistics of differential fading, which is the difference between amplitudes of the direct wave and interference wave, both affected by multipath fading.
FIGURE 5..[068005] = xx cm
A practical prediction method for the statistics of signaltointerference ratio where the effect of thermal noise and timevariant interference is taken into account is provided below.
5.2 Prediction method
In general there are two kinds of interference between adjacent satellite systems. One is “downlink interference” on the mobile earth station side, and the other is “uplink interference” on the satellite side. Another situation is interference between beams in multispotbeam operation, where the same frequency is allocated repeatedly. The method is applicable to such cases.
Input parameters (in units of power, not dB) are:
D : power of the direct wave component of desired signal
M : average power of the reflected component (i.e. incoherent component) of desired signal
N : average power of system noise
I_{D} : power of the direct wave component of interference signal
I_{M} : average power of reflected component of interference signal
(I : average power of interference: I I_{D} I_{M})
Output parameters (in units of power, not dB) are:
[c / n](p) : ratio of desired signal power to system noise power as a function of time percentage p
[c / i](p) : ratio of desired signal power to interfering signal power
[c / (i n)] (p) : ratio of desired signal power to system noise plus interfering signal power.
Carriertonoise ratio as a function of p is given by:
[ c / n ]( p) (_{c})^{2} ( p) D / N (5)
where _{c} is the normalized timepercentagedependent factor of desired signal power having a probability density function of a NakagamiRice distribution with constant direct power given in Fig. 3, in which:
20 log _{c} A 10 log ((D M) / D) (6)
where A is amplitude (dB) read from the ordinate of Fig. 3. The parameter in the figure for this application is M / (D M).
The signaltointerference ratio as a function of p is given by:
[c / i]( p) (_{c}_{ }_{/}_{ }_{i})^{2}( p) D / I_{50} (7)
where I_{50} is the median value (i.e. value for 50% of the time) of power variations of the interference signal:
I_{50} (_{i}_{,50})^{2} I (8)
and _{c}_{ }_{/}_{ }_{i} is the normalized timepercentagedependent factor of [c / i] variations approximately given by:
[log _{c}_{ }_{/}_{ }_{i}( p)]^{2} [log _{c}( p)]^{2} [log _{i}(100 – p)]^{2} (9)
where _{i} is the normalized timepercentagedependent factor of interference signal power. A solution where _{c}_{ }_{/}_{ }_{i} 1 should be selected for the time percentage satisfying _{c} 1 and _{i} 1. By setting I_{D}_{ }/ I b, _{I}_{,50} and _{i} (both in dB) as a function of b are given in Table 3.
Finally,
[c / (i n)] ( p) [1 / [c / n]( p) 1 / [c / i]( p)]^{–1} (10)
Prediction accuracy of the method for [c / i] and [c / (n i)] is within 1 dB for all cases within the following parameter range:
N – 5 dB; M – 5 dB; I – 10 dB; 0.5 b 1 (11)
where all quantities are relative to D.
TABLE 3
Values of _{i} and _{I}_{,50} as functions of time percentage ( p) and b = [I_{D}_{ }/_{ }(I_{D} I_{M})]
b

I_{M}_{ }/ I_{D}

_{I}_{,50}

_{i} (dB)


(dB)

(dB)

p(%)
50

20

10

5

1

0.5

0.1

0.01

0


1.59

0.00

3.66

5.21

6.36

8.22

8.83

9.98

11.25

0.5

0

1.12

0.00

3.16

4.48

5.44

7.03

7.54

8.52

9.60

0.6

1.8

0.91

0.00

2.88

4.09

4.99

6.46

6.95

7.87

8.90

0.7

3.7

0.68

0.00

2.53

3.62

4.43

5.78

6.22

7.08

8.03

0.8

6.0

0.45

0.00

2.10

3.03

3.72

4.90

5.30

6.07

6.92

0.9

9.5

0.22

0.00

1.52

2.21

2.76

3.69

4.00

4.62

5.32

0.95

12.8

0.11

0.00

1.09

1.61

2.02

2.74

2.99

3.48

4.02

1.0


0.00

0.00

0.00

0.00

0.00

0.00

0.00

0.00

0.00
 